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lt1800 1 1800fa typical application description 80mhz, 25v/s low power rail-to-rail input and output precision op amp the lt ? 1800 is a low power, high speed rail-to-rail input and output operational ampli? er with excellent dc performance. the lt1800 features reduced supply current, lower input offset voltage, lower input bias current and higher dc gain than other devices with comparable bandwidth. the lt1800 has an input range that includes both supply rails and an output that swings within 20mv of either supply rail to maximize the signal dynamic range in low supply applications. the lt1800 maintains its performance for supplies from 2.3v to 12.6v and is speci? ed at 3v, 5v and 5v supplies. the inputs can be driven beyond the supplies without damage or phase reversal of the output. the lt1800 is available in the 8-pin so package with the standard op amp pinout and in the 5-pin tsot-23 package. for dual and quad versions of the lt1800, see the lt1801/lt1802 data sheet. the lt1800 can be used as a plug-in replacement for many op amps to improve input/output range and performance. single supply 1a laser driver ampli? er features applications n gain bandwidth product: 80mhz n input common mode range includes both rails n output swings rail-to-rail n low quiescent current: 2ma max n input offset voltage: 350v max n input bias current: 250na max n low voltage noise: 8.5nv/ hz n slew rate: 25v/s n common mode rejection: 105db n power supply rejection: 97db n open-loop gain: 85v/mv n operating temperature range: C40c to 85c n available in the 8-pin so and 5-pin low pro? le (1mm) thinsot? packages n low voltage, high frequency signal processing n driving a/d converters n rail-to-rail buffer ampli? ers n active filters n video line driver l , lt, ltc, ltm, linear technology and the linear logo are registered trademarks of linear technology corporation. thinsot is a trademark of linear technology corporation. all other trademarks are the property of their respective owners. laser driver ampli? er 500ma pulse response + C lt1800 v in do not float ir laser infineon sfh495 q1 zetex fmmt619 5v r2 330 r1 1 1800 ta01a c1 39pf r3 10 1800 ta01b 50ns/div 100ma/div
lt1800 2 1800fa absolute maximum ratings total supply voltage (v s C to v s + ) ..........................12.6v input current (note 2) ..........................................10ma output short-circuit duration (note 3) ............ inde? nite operating temperature range (note 4).... C40c to 85c (note 1) 1 2 3 4 8 7 6 5 top view nc v s + v out nc nc Cin +in v s C s8 package 8-lead plastic so + C t jmax = 150c, ja = 190c/w v out 1 v s C 2 top view s5 package 5-lead plastic tsot-23 +in 3 5 v s + 4 Cin + C t jmax = 150c, ja = 250c/w pin configuration order information lead free finish tape and reel part marking package description specified temperature range lt1800cs8#pbf lt1800cs8#trpbf 1800 8-lead plastic so 0c to 70c lt1800is8#pbf lt1800is8#trpbf 1800i 8-lead plastic so C40c to 85c lt1800cs5#pbf lt1800cs5#trpbf ltrn 5-lead plastic tsot-23 0c to 70c lt1800is5#pbf lt1800is5#trpbf ltrp 5-lead plastic tsot-23 C40c to 85c consult ltc marketing for parts speci? ed with wider operating temperature ranges. consult ltc marketing for information on non-standard lead based ? nish parts. for more information on lead free part marking, go to: http://www.linear.com/leadfree/ for more information on tape and reel speci? cations, go to: http://www.linear.com/tapeandreel/ speci? ed temperature range (note 5) .... C40c to 85c junction temperature ........................................... 150c storage temperature range ................... C65c to 150c lead temperature (soldering, 10 sec).................. 300c symbol parameter conditions min typ max units v os input offset voltage v cm = 0v v cm = 0v (sot-23) v cm = v s v cm = v s (sot-23) 75 300 0.5 0.7 350 750 3 3.5 v v mv mv v os input offset shift v cm = 0v to v s C 1.5v 20 180 v i b input bias current v cm = 1v v cm = v s 25 500 250 1500 na na i os input offset current v cm = 1v v cm = v s 25 25 200 200 na na input noise voltage 0.1hz to 10hz 1.4 v p-p electrical characteristics t a = 25c. v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted.
lt1800 3 1800fa electrical characteristics t a = 25c. v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. symbol parameter conditions min typ max units e n input noise voltage density f = 10khz 8.5 nv/ hz i n input noise current density f = 10khz 1 pa/ hz c in input capacitance f = 100khz 2 pf a vol large-signal voltage gain v s = 5v, v o = 0.5v to 4.5v, r l = 1k at v s /2 v s = 5v, v o = 1v to 4v, r l = 100 at v s /2 v s = 3v, v o = 0.5v to 2.5v, r l = 1k at v s /2 35 3.5 30 85 8 85 v/mv v/mv v/mv cmrr common mode rejection ratio v s = 5v, v cm = 0v to 3.5v v s = 3v, v cm = 0v to 1.5v 85 78 105 97 db db input common mode range 0 v s v psrr power supply rejection ratio v s = 2.5v to 10v, v cm = 0v 80 97 db minimum supply voltage (note 6) 2.3 2.5 v v ol output voltage swing low (note 7) no load i sink = 5ma i sink = 20ma 12 80 225 50 160 450 mv mv mv v oh output voltage swing high (note 7) no load i source = 5ma i source = 20ma 16 120 450 60 250 850 mv mv mv i sc short-circuit current v s = 5v v s = 3v 20 20 45 40 ma ma i s supply current per ampli? er 1.6 2 ma gbw gain bandwidth product frequency = 2mhz 40 80 mhz sr slew rate v s = 5v, a v = C1, r l = 1k, v o = 4v 13 25 v/s fpbw full power bandwidth v s = 5v, v out = 4v p-p 2 mhz hd harmonic distortion v s = 5v, a v = 1, r l = 1k, v o = 2v p-p , f c = 500khz C75 dbc t s settling time 0.01%, v s = 5v, v step = 2v, a v = 1, r l = 1k 250 ns g differential gain (ntsc) v s = 5v, a v = +2, r l = 150 0.35 % ? differential phase (ntsc) v s = 5v, a v = +2, r l = 150 0.4 deg the l denotes the speci? cations which apply over the temperature range of 0c t a 70c. v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. symbol parameter conditions min typ max units v os input offset voltage v cm = 0v v cm = 0v (sot-23) v cm = v s v cm = v s (sot-23) l l l l 125 300 0.6 0.7 500 1250 3.5 3.75 v v mv mv v os input offset shift v cm = 0v to v s C 1.5v l 30 275 v v os tc input offset voltage drift (note 8) l 1.5 5 v/c i b input bias current v cm = 1v v cm = v s C 0.2v l l 50 550 300 1750 na na i os input offset current v cm = 1v v cm = v s C 0.2v l l 25 25 250 250 na na a vol large-signal voltage gain v s = 5v, v o = 0.5v to 4.5v, r l = 1k at v s /2 v s = 5v, v o = 1v to 4v, r l = 100 at v s /2 v s = 3v, v o = 0.5v to 2.5v, r l = 1k at v s /2 l l l 30 3 25 75 6 75 v/mv v/mv v/mv cmrr common mode rejection ratio v s = 5v, v cm = 0v to 3.5v v s = 3v, v cm = 0v to 1.5v l l 82 74 101 93 db db
lt1800 4 1800fa electrical characteristics the l denotes the speci? cations which apply over the temperature range of 0c t a 70c. c. v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. symbol parameter conditions min typ max units v os input offset voltage v cm = 0v v cm = 0v (sot-23) v cm = v s v cm = v s (sot-23) l l l l 175 400 0.75 0.9 700 2000 4 4 v v mv mv v os input offset shift v cm = 0v to v s C 1.5v l 30 300 v v os tc input offset voltage drift (note 8) l 1.5 5 v/c i b input bias current v cm = 1v v cm = v s C 0.2v l l 50 600 400 2000 na na i os input offset current v cm = 1v v cm = v s C 0.2v l l 25 25 300 300 na na a vol large-signal voltage gain v s = 5v, v o = 0.5v to 4.5v, r l = 1k at v s /2 v s = 5v, v o = 1.5v to 3.5v, r l = 100 at v s /2 v s = 3v, v o = 0.5v to 2.5v, r l = 1k at v s /2 l l l 25 2.5 20 65 6 65 v/mv v/mv v/mv cmrr common mode rejection ratio v s = 5v, v cm = 0v to 3.5v v s = 3v, v cm = 0v to 1.5v l l 81 73 101 93 db db input common mode range l 0v s v psrr power supply rejection ratio v s = 2.5v to 10v, v cm = 0v l 73 90 db minimum supply voltage (note 6) l 2.3 2.5 v v ol output voltage swing low (note 7) no load i sink = 5ma i sink = 10ma l l l 15 105 170 70 210 400 mv mv mv v oh output voltage swing high (note 7) no load i source = 5ma i source = 10ma l l l 25 150 300 90 350 700 mv mv mv i sc short-circuit current v s = 5v v s = 3v l l 12.5 12.5 30 30 ma ma i s supply current per ampli? er l 2.1 3 ma gbw gain bandwidth product frequency = 2mhz l 30 70 mhz sr slew rate v s = 5v, a v = C 1, r l = 1k, v o = 4v l 10 18 v/s the l denotes the speci? cations which apply over the temperature range of C40c t a 85c. v s = 5v, 0v; v s = 3v, 0v; v cm = v out = half supply, unless otherwise noted. symbol parameter conditions min typ max units input common mode range l 0v s v psrr power supply rejection ratio v s = 2.5v to 10v, v cm = 0v l 74 91 db minimum supply voltage (note 6) l 2.3 2.5 v v ol output voltage swing low (note 7) no load i sink = 5ma i sink = 20ma l l l 14 100 300 60 200 550 mv mv mv v oh output voltage swing high (note 7) no load i source = 5ma i source = 20ma l l l 25 150 600 80 300 1000 mv mv mv i sc short-circuit current v s = 5v v s = 3v l l 20 20 40 30 ma ma i s supply current per ampli? er l 2 2.75 ma gbw gain bandwidth product frequency = 2mhz l 35 75 mhz sr slew rate v s = 5v, a v = C 1, r l = 1k, v o = 4v p-p l 11 22 v/s
lt1800 5 1800fa electrical characteristics t a = 25c, v s = 5v, v cm = 0v, v out = 0v, unless otherwise noted. symbol parameter conditions min typ max units v os input offset voltage v cm = v s C v cm = v s C (sot-23) v cm = v s + v cm = v s + (sot-23) 150 400 0.7 1 500 1000 3.5 4.5 v v mv mv v os input offset shift v cm = v s C to v s + C 1.5v 30 475 v i b input bias current v cm = v s C + 1v v cm = v s + 25 400 350 1500 na na i os input offset current v cm = v s C + 1v v cm = v s + 20 20 250 250 na na input noise voltage 0.1hz to 10hz 1.4 v p-p e n input noise voltage density f = 10khz 8.5 nv/ hz i n input noise current density f = 10khz 1 pa/ hz c in input capacitance f = 100khz 2 pf a vol large-signal voltage gain v o = C4v to 4v, r l = 1k v o = C2v to 2v, r l = 100 25 2.5 70 7 v/mv v/mv cmrr common mode rejection ratio v cm = v s C to 3.5v 85 109 db input common mode range v s C v s + v psrr power supply rejection ratio v s + = 2.5v to 10v, v s C = 0v 80 97 db v ol output voltage swing low (note 7) no load i sink = 5ma i sink = 20ma 15 85 225 60 170 450 mv mv mv v oh output voltage swing high (note 7) no load i source = 5ma i source = 20ma 17 130 450 70 260 900 mv mv mv i sc short-circuit current 30 50 ma i s supply current per ampli? er 1.8 2.75 ma gbw gain bandwidth product frequency = 2mhz 70 mhz sr slew rate a v = C 1, r l = 1k, v o = 4v, measured at v o = 2v 23 v/s fpbw full power bandwidth v o = 8v p-p 0.9 mhz hd harmonic distortion a v = 1, r l = 1k, v o = 2v p-p , f c = 500khz C75 dbc t s settling time 0.01%, v step = 5v, a v = 1v, r l = 1k 300 ns g differential gain (ntsc) a v = + 2, r l = 150 0.35 % ? differential phase (ntsc) a v = + 2, r l = 150 0.2 deg the l denotes the speci? cations which apply over the temperature range of 0c t a 70c. v s = 5v, v cm = 0v, v out = 0v, unless otherwise noted. symbol parameter conditions min typ max units v os input offset voltage v cm = v s C v cm = v s C (sot-23) v cm = v s + v cm = v s + (sot-23) l l l l 200 450 0.75 1 800 1500 4 5 v v mv mv v os input offset shift v cm = v s C to v s + C 1.5v l 45 675 v v os tc input offset voltage drift (note 8) l 1.5 5 v/c i b input bias current v cm = v s C + 1v v cm = v s + C 0.2v l l 30 450 400 1750 na na
lt1800 6 1800fa electrical characteristics the l denotes the speci? cations which apply over the temperature range of 0c t a 70c. v s = 5v, v cm = 0v, v out = 0v, unless otherwise noted. the l denotes the speci? cations which apply over the temperature range of C40c t a 85c. v s = 5v, v cm = 0v, v out = 0v, unless otherwise noted. symbol parameter conditions min typ max units v os input offset voltage v cm = v s C v cm = v s C (sot-23) v cm = v s + v cm = v s + (sot-23) l l l l 350 500 0.75 1 900 2250 4.5 5.5 v v mv mv v os input offset shift v cm = v s C to v s + C 1.5v l 50 750 v v os tc input offset voltage drift (note 8) l 1.5 5 v/c i b input bias current v cm = v s C + 1v v cm = v s + C 0.2v l l 50 450 450 2000 na na i os input offset current v cm = v s C + 1v v cm = v s + C 0.2v l l 25 25 350 350 na na a vol large-signal voltage gain v o = C4v to 4v, r l = 1k v o = C1v to 1v, r l = 100 l l 16 2 55 5 v/mv v/mv cmrr common mode rejection ratio v cm = v s C to 3.5v l 81 104 db input common mode range l v s C v s + v psrr power supply rejection ratio v s + = 2.5v to 10v, v s C = 0v l 73 90 db v ol output voltage swing low (note 7) no load i sink = 5ma i sink = 10ma l l l 15 105 170 80 220 400 mv mv mv v oh output voltage swing high (note 7) no load i source = 5ma i source = 10ma l l l 25 150 300 100 350 700 mv mv mv i sc short-circuit current l 12.5 30 ma i s supply current per ampli? er l 2.6 4 ma gbw gain bandwidth product frequency = 2mhz l 65 mhz sr slew rate a v = C1, r l = 1k, v o = 4v, measured at v o = 2v l 15 v/s symbol parameter conditions min typ max units i os input offset current v cm = v s C + 1v v cm = v s + C 0.2v l l 25 25 300 300 na na a vol large-signal voltage gain v o = C4v to 4v, r l = 1k v o = C2v to 2v, r l = 100 l l 20 2 55 5 v/mv v/mv cmrr common mode rejection ratio v cm = v s C to 3.5v l 82 105 db input common mode range l v s C v s + v psrr power supply rejection ratio v s + = 2.5v to 10v, v s C = 0v l 74 91 db v ol output voltage swing low (note 7) no load i sink = 5ma i sink = 20ma l l l 17 105 250 70 210 575 mv mv mv v oh output voltage swing high (note 7) no load i source = 5ma i source = 20ma l l l 25 150 600 90 310 1100 mv mv mv i sc short-circuit current l 25 45 ma i s supply current per ampli? er l 2.4 3.5 ma gbw gain bandwidth product frequency = 2mhz l 70 mhz sr slew rate a v = C1, r l = 1k, v o = 4v, measured at v o = 2v l 20 v/s
lt1800 7 1800fa note 1: stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. exposure to any absolute maximum rating condition for extended periods may affect device reliability and lifetime. note 2: the inputs are protected by back-to-back diodes and by esd diodes to the supply rails. if the differential input voltage exceeds 1.4v or either input goes outside the rails, the input current should be limited to less than 10ma. note 3: a heat sink may be required to keep the junction temperature below the absolute maximum rating when the output is shorted inde? nitely. note 4: the lt1800c/lt1800i are guaranteed functional over the temperature range of C40c to 85c. note 5: the lt1800c is guaranteed to meet speci? ed performance from 0c to 70c. the lt1800c is designed, characterized and expected to meet speci? ed performance from C40c to 85c but is not tested or qa sampled at these temperatures. the lt1800i is guaranteed to meet speci? ed performance from C40c to 85c. note 6: minimum supply voltage is guaranteed by power supply rejection ratio test. note 7: output voltage swings are measured between the output and power supply rails. note 8: this parameter is not 100% tested. electrical characteristics v os distribution, v cm = 0v (so-8, pnp stage) v os distribution, v cm = 5v (so-8, npn stage) v os distribution, v cm = 0v (sot-23, pnp stage) v os distribution, v cm = 5v (sot-23, npn stage) supply current vs supply voltage offset voltage vs input common mode voltage typical performance characteristics input offset voltage (v) C250 0 percent of units (%) 5 15 20 25 50 150 45 1800 g01 10 C150 C50 250 30 35 40 v s = 5v, 0v v cm = 0v input offset voltage (v) C2000 0 percent of units (%) 5 15 20 25 400 1200 45 1800 g02 10 C1200 C400 2000 30 35 40 v s = 5v, 0v v cm = 5v input offset voltage (v) C1250 percent of units (%) 40 35 30 25 20 15 10 5 0 750 1800 g03 C750 C250 250 1250 v s = 5v, 0v v cm = 0v input offset voltage (v) C2500 0 percent of units (%) 5 15 20 25 35 1800 g04 10 30 C500 2500 C1500 500 1500 v s = 5v, 0v v cm = 5v total supply voltage (v) 1 0 supply current (ma) 3 12 1800 g05 0 357910 2468 11 4 2 1 t a = 125c t a = 25c t a = C55c input common mode voltage (v) 0 offset voltage (v) 100 300 500 4 1800 g06 C100 C300 0 200 400 C200 C400 C500 1 2 3 5 v s = 5v, 0v typical part t a = C55c t a = 125c t a = 25c
lt1800 8 1800fa typical performance characteristics output saturation voltage vs load current (output high) minimum supply voltage output short-circuit current vs power supply voltage open-loop gain open-loop gain open-loop gain input bias current vs common mode voltage input bias current vs temperature output saturation voltage vs load current (output low) input common mode voltage (v) C1 input bias current (a) 0.2 0.6 1.0 4 1800 g07 C0.2 C0.6 0 0.4 0.8 C0.4 C0.8 C1.0 0 1 23 5 6 v s = 5v, 0v t a = 25c t a = 125c t a = C55c temperature (c) C60 C0.1 input bias (a) 0 0.2 0.3 0.4 40 60 80 0.8 1800 g08 0.1 C40 C20 0 20 0.5 0.6 0.7 npn active v s = 5v, 0v v cm = 5v pnp active v s = 5v, 0v v cm = 1v load current (ma) 0.01 0.1 0.001 output saturation voltage (v) 0.1 10 1 10 100 1800 g09 0.01 1 v s = 5v, 0v t a = 125c t a = C55c t a = 25c load current (ma) 0.01 0.1 0.001 output saturation voltage (v) 0.1 10 1 10 100 1800 g10 0.01 1 v s = 5v, 0v t a = 125c t a = C55c t a = 25c total supply voltage (v) 0 C0.6 change in offset voltage (mv) C0.4 0 0.2 0.4 2 3 3.5 5.5 1800 g11 C0.2 1.5 2.5 4 4.5 5 0.6 t a = 125c t a = C55c t a = 25c power supply voltage (v) 1.5 C70 output short-circuit current (ma) C50 C30 C10 70 30 2 3 3.5 5 50 10 C60 C40 C20 60 20 40 0 2.5 4 4.5 t a = 125c t a = 125c t a = C55c sinking v s = 5v, 0v sourcing t a = C55c t a = 25c t a = 25c 1800 g12 output voltage (v) 0 C2000 change in offset voltage (v) C1200 C400 400 0.5 1 1.5 2 1800 g13 2.5 1200 2000 C1600 C800 0 800 1600 3 v s = 3v, 0v r l to gnd r l = 1k r l = 100 output voltage (v) 0 change in offset voltage (v) 400 1200 2000 4 1800 g14 C400 C1200 0 800 1600 C800 C1600 C2000 1 0.5 2 1.5 3 3.5 4.5 2.5 5 v s = 5v, 0v r l to gnd r l = 1k r l = 100 output voltage (v) C5 change in offset voltage (v) 400 1200 2000 3 1800 g15 C400 C1200 0 800 1600 C800 C1600 C2000 C3 C4 C1 C2 12 4 0 5 v s = 5v r l to gnd r l = 1k r l = 100
lt1800 9 1800fa typical performance characteristics input current noise vs frequency 0.1hz to 10hz output voltage noise gain bandwidth and phase margin vs supply voltage gain bandwidth and phase margin vs temperature offset voltage vs output current warm-up drift vs time (lt1800s8) input noise voltage vs frequency output current (ma) C60 change in offset voltage (mv) 0 1.0 60 1800 g16 C1.0 C2.0 C30 0 30 C45 C15 15 45 2.0 C0.5 0.5 C1.5 1.5 v s = 5v t a = 125c t a = C55c t a = 25c time after power-up (seconds) 0 offset voltage (v) 110 60 1800 g17 80 60 20 40 80 50 40 120 100 90 70 100 120 140 v s = 5v v s = 2.5v v s = 1.5v typical part frequency (khz) 20 noise voltage (nv/ hz ) 40 60 10 30 50 0.01 1 10 100 1800 g18 0 0.1 v s = 5v, 0v npn active v cm = 4.25v pnp active v cm = 2.5v frequency (khz) 1.0 noise current (pa/ hz ) 2.0 3.0 0.5 1.5 2.5 0.01 1 10 100 1800 g19 0 0.1 v s = 5v, 0v npn active v cm = 4.25v pnp active v cm = 2.5v time (seconds) 0 output noise voltage (nv) 2000 1000 0 C1000 C2000 8 1800 g20 246 10 7 135 9 v s = 5v, 0v total supply voltage (v) 0 gain bandwidth (mhz) phase margin (deg) 100 90 80 70 60 60 50 40 30 20 8 1800 g21 246 10 7 135 9 gain bandwidth product phase margin t a = 25c temperature (c) C55 gain bandwidth (mhz) phase margin (deg) 50 100 70 C15 25 45 125 1800 g22 80 90 60 10 20 40 50 60 30 C35 5 65 85 105 gbw product v s = 2.5v phase margin v s = 2.5v phase margin v s = 5v gbw product v s = 5v
lt1800 10 1800fa typical performance characteristics common mode rejection ratio vs frequency power supply rejection ratio vs frequency series output resistor vs capacitive load gain vs frequency (a v = 1) gain vs frequency (a v = 2) output impedance vs frequency frequency (mhz) C6 gain (db) 0 3 9 12 0.1 10 100 300 1800 g25 C12 1 6 C3 C9 r l = 1k c l = 10pf a v = 1 v s = 5v v s = 2.5v frequency (mhz) 0 gain (db) 6 9 15 18 0.1 10 100 300 1800 g26 C6 1 12 3 C3 r l = 1k c l = 10pf a v = 2 v s = 5v v s = 2.5v frequency (mhz) 0.1 0.001 output impedance () 0.1 600 100 1 10 100 500 1800 g27 0.01 1 10 v s = 2.5v a v = 10 a v = 1 a v = 2 frequency (mhz) 40 common mode rejection ratio (db) 80 120 20 60 100 0.01 1 10 100 1800 g28 0 0.1 v s = 5v, 0v frequency (mhz) 0.001 30 power supply rejection ratio (db) 40 50 60 70 0.01 0.1 1 10 100 1800 g29 20 10 0 C10 80 90 v s = 5v, 0v t a = 25c positive supply negative supply capacitive load (pf) 10 20 overshoot (%) 30 40 100 1000 10000 1800 g30 10 0 60 50 15 25 35 5 55 45 v s = 5v, 0v a v = 1 r os = 10 r os = 20 r os = r l = 50 slew rate vs temperature gain and phase vs frequency temperature ( o c) C55 10 slew rate (v/s) 15 25 30 35 C15 25 45 125 1800 g23 20 C35 5 65 85 105 a v = C1 r f = r g = 1k r l = 1k v s = 2.5v v s = 5v frequency (mhz) 0.01 10 open-loop gain (db) phase (deg) 20 30 40 50 0.1 1 10 100 300 1800 g24 0 C40 C10 C20 C30 60 70 C20 0 20 40 60 C60 C80 C100 80 100 v s = 2.5v v s = 5v phase gain
lt1800 11 1800fa typical performance characteristics 5v large-signal response 5v small-signal response output overdriven recovery maximum undistorted output signal vs frequency 5v large-signal response 5v small-signal response series output resistor vs capacitive load distortion vs frequency distortion vs frequency capacitive load (pf) 10 20 overshoot (%) 30 40 100 1000 10000 1800 g31 10 0 60 50 15 25 35 5 55 45 v s = 5v, 0v a v = 2 r os = 10 r os = r l = 50 r os = 20 frequency (mhz) 0.01 C70 distortion (dbc) C60 C50 C40 0.1 1 10 1800 g32 C80 C90 C100 C110 v s = 5v, 0v a v = 1 v out = 2v p-p r l = 150 7 , 2nd r l = 150, 3rd r l = 1k, 2nd r l = 1k, 3rd frequency (mhz) 0.01 C70 distortion (dbc) C60 C50 C40 0.1 1 10 1800 g33 C80 C90 C100 C110 v s = 5v, 0v a v = 2 v out = 2v p-p r l = 150, 2nd r l = 150, 3rd r l = 1k, 2nd r l = 1k, 3rd frequency (hz) 4.1 output voltage swing (v p-p ) 4.3 4.5 4.6 1k 100k 1m 10m 1800 g34 3.9 10k 4.4 4.2 4.0 v s = 5v, 0v r l = 1k a v = C1 a v = 2 100ns/div 1v/div 0v 1800 g35 v s = 5v, 0v a v = 1 r l = 1k 50ns/div 50mv/div 0v 1800 g36 v s = 5v, 0v a v = 1 r l = 1k 200ns/div 2v/div 0v 1800 g37 v s = 5v a v = 1 r l = 1k 50ns/div 50mv/div 0v 1800 g38 v s = 5v a v = 1 r l = 1k 100ns/div v out 2v/div 0v v in 1v/div 0v 1800 g39 v s = 5v, 0v a v = 2 r l = 1k
lt1800 12 1800fa applications information circuit description the lt1800 has an input and output signal range that cov- ers from the negative power supply to the positive power supply. figure 1 depicts a simpli? ed schematic of the ampli? er. the input stage is comprised of two differential ampli? ers, a pnp stage q1/q2 and an npn stage q3/q4 that are active over the different ranges of common mode input voltage. the pnp differential pair is active between the negative supply to approximately 1.2v below the positive supply. as the input voltage moves closer toward the posi- tive supply, the transistor q5 will steer the tail current i 1 to the current mirror q6/q7, activating the npn differential pair and the pnp pair becomes inactive for the rest of the input common mode range up to the positive supply. also at the input stage, devices q17 to q19 act to cancel the bias current of the pnp input pair. when q1-q2 are active, the current in q16 is controlled to be the same as the current in q1-q2, thus the base current of q16 is nominally equal to the base current of the input devices. the base current of q16 is then mirrored by devices q17-q19 to cancel the base current of the input devices q1-q2. a pair of complementary common emitter stages q14/q15 that enable the output to swing from rail to rail constructs the output stage. the capacitors c2 and c3 form the lo- cal feedback loops that lower the output impedance at high frequency. these devices are fabricated on linear technologys proprietary high speed complementary bipolar process. power dissipation the lt1800 ampli? er is offered in a small package, sot-23, which has a thermal resistance of 250c/w, ja . so there is a need to ensure that the dies junction temperature should not exceed 150c. junction temperature t j is calculated from the ambient temperature t a , power dissipation p d and thermal resistance ja : t j = t a + (p d ? ja ) the power dissipation in the ic is the function of the sup- ply voltage, output voltage and the load resistance. for a given supply voltage, the worst-case power dissipation p dmax occurs at the maximum supply current and the q4 q18 q17 q16 q6 q3 q7 q10 q1 q13 q15 out q2 q11 q12 q9 q5 v bias i 1 d2 d1 d5 d4 d3 d6 d7 d8 esdd2 esdd1 +in Cin v C esdd3 esdd4 v + v + v C q8 r2 r1 r3 r4 r5 q14 1800 f01 + i 2 + i 3 c2 c c v C + c1 buffer and output bias v + v C q19 figure 1. lt1800 simpli? ed schematic diagram
lt1800 13 1800fa applications information output voltage is at half of either supply voltage (or the maximum swing is less than 1/2 supply voltage). p dmax is given by: p dmax = (v s ? i smax ) + (v s /2) 2 /r l example: an lt1800 in a sot-23 package operating on 5v supplies and driving a 50 load, the worst-case power dissipation is given by: p dmax = (10 ? 4ma) + (2.5) 2 /50 = 0.04 + 0.125 = 0.165w the maximum ambient temperature that the part is al- lowed to operate is: t a = t j C (p dmax ? 250c/w) = 150c C (0.165w ? 250c/w) = 108c input offset voltage the offset voltage will change depending upon which input stage is active. the pnp input stage is active from the negative supply rail to 1.2v of the positive supply rail, then the npn input stage is activated for the remaining input range up to the positive supply rail during which the pnp stage remains inactive. the offset voltage is typically less than 75v in the range that the pnp input stage is active. input bias current the lt1800 employs a patent-pending technique to trim the input bias current to less than 250na for the input common mode voltage of 0.2v above negative supply rail to 1.2v of the positive rail. the low input offset volt- age and low input bias current of the lt1800 provide the precision performance especially for high source imped- ance applications. output the lt1800 can deliver a large output current, so the short- circuit current limit is set around 50ma to prevent damage to the device. attention must be paid to keep the junction temperature of the ic below the absolute maximum rating of 150c (refer to the power dissipation section) when the output is continuously short-circuited. the output of the ampli? er has reverse-biased diodes connected to each sup- ply. if the output is forced beyond either supply, unlimited current will ? ow through these diodes. if the current is transient and limited to several hundred ma, and the total supply voltage is less than 12.6v, the absolute maximum rating, no damage will occur to the device. overdrive protection when the input voltage exceeds the power supplies, two pairs of crossing diodes d1 to d4 will prevent the output from reversing polarity. if the input voltage exceeds either power supply by 700mv, diode d1/d2 or d3/d4 will turn on to keep the output at the proper polarity. for the phase reversal protection to perform properly, the input current must be limited to less than 10ma. if the ampli? er is severely overdriven, an external resistor should be used to limit the overdrive current. the lt1800s input stages are also protected against a large differential input voltage of 1.4v or higher by a pair of back-back diodes d5/d8 to prevent the emitter-base breakdown of the input transistors. the current in these diodes should be limited to less than 10ma when they are active. the worst-case differential input voltage usually occurs when the input is driven while the output is shorted to ground in a unity gain con? guration. in addition, the ampli? er is protected against esd strikes up to 3kv on all pins by a pair of protection diodes on each pin that are connected to the power supplies as shown in figure 1. capacitive load the lt1800 is optimized for high bandwidth, low power and precision applications. it can drive a capacitive load of about 75pf in a unity gain con? guration, and more for higher gain. when driving a larger capacitive load, a resistor of 10 to 50 should be connected between the output and the capacitive load to avoid ringing or oscillation. the feedback should still be taken from the output so that the resistor will isolate the capacitive load to ensure stability. graphs on capacitive loads indicate the transient response of the ampli? er when driving capacitive load with a speci- ? ed series resistor.
lt1800 14 1800fa single supply 1a laser driver ampli? er the circuit in the front page of this data sheet shows the lt1800 used in a 1a laser driver application. one of the reasons the lt1800 is well suited to this control task is that its 2.3v operation ensures that it will be awake during power-up and operated before the circuit can otherwise cause signi? cant current to ? ow in the 2.1v threshold laser diode. driving the noninverting input of the lt1800 to a voltage v in will control the turning on of the high current npn transistor, fmmt619 and the laser diode. a current equal to v in /r1 ? ows through the laser diode. the lt1800 low offset voltage and low input bias current allows it to control the current that ? ows through the laser diode precisely. the overall circuit is a 1a per volt v-to-i converter. frequency compensation components r2 and c1 are selected for fast but zero-overshoot time domain response to avoid overcurrent conditions in the laser. the time domain response of this circuit, measured at r1 and given a 500mv 230ns input pulse, is also shown in the graphic on the front page. while the circuit is capable of 1a operation, the laser diode and the transistor are thermally limited due to power dissipation, so they must be operated at low duty cycles. fast 1a current sense ampli? er a simple, fast current sense ampli? er in figure 2 is suitable for quickly responding to out-of-range currents. the circuit ampli? es the voltage across the 0.1 sense resistor by a gain of 20, resulting in a conversion gain of 2v/a. the C3db bandwidth of the circuit is 4mhz, and the uncertainty due to v os and i b is less than 4ma. the minimum output voltage is 60mv, corresponding to 30ma. the large-signal response of the circuit is shown in figure 3. applications information feedback components when feedback resistors are used to set up gain, care must be taken to ensure that the pole formed by the feedback resistors and the total capacitance at the inverting input does not degrade stability. for instance, the lt1800 in a noninverting gain of 2, set up with two 5k resistors and a capacitance of 5pf (part plus pc board) will probably ring in transient response. the pole is formed at 12.7mhz that will reduce phase margin by 32 degrees when the crossover frequency of the ampli? er is around 20mhz. a capacitor of 5pf or higher connected across the feedback resistor will eliminate any ringing or oscillation. typical applications + C lt1800 0.1 i l 0a to 1a v out 0v to 2v v out = 2 ? i l f C3db = 4mhz uncertainty due to v os, i b < 4ma 3v 1k 1800 f02 52.3 52.3 figure 2. fast 1a current sense figure 3. current sense ampli? er large-signal response 1800 f03 50ns/div v s = 3v 500mv/div 0v
lt1800 15 1800fa typical applications single 3v supply, 1mhz, 4th order butterworth filter the circuit shown in figure 4 makes use of the low voltage operation and the wide bandwidth of the lt1800 to create a dc accurate 1mhz 4th order lowpass ? lter powered from a 3v supply. the ampli? ers are con? gured in the inverting mode for the lowest distortion and the output can swing rail-to-rail for maximum dynamic range. figure 5 displays the frequency response of the ? lter. stopband attenuation is greater than 100db at 50mhz. with a 2.25v p-p , 250khz input signal, the ? lter has harmonic distortion products of less than C85dbc. worst-case output offset voltage is less than 6mv. figure 4. 3v, 1mhz, 4th order butterworth filter figure 5. frequency response of filter C + lt1800 909 v in v s /2 v out 1800 f04 220pf 909 2.67k C + lt1800 1.1k 22pf 3v 470pf 2.21k 1.1k 47pf frequency (hz) C80 gain (db) C40 0 C100 C60 C20 1k 100k 1m 10m 100m 1800 f05 C120 10k
lt1800 16 1800fa package description s5 package 5-lead plastic tsot-23 (reference ltc dwg # 05-08-1635) 1.50 ?1.75 (note 4) 2.80 bsc 0.30 ?0.45 typ 5 plcs (note 3) datum ? 0.09 ?0.20 (note 3) s5 tsot-23 0302 rev b pin one 2.90 bsc (note 4) 0.95 bsc 1.90 bsc 0.80 ?0.90 1.00 max 0.01 ?0.10 0.20 bsc 0.30 ?0.50 ref note: 1. dimensions are in millimeters 2. drawing not to scale 3. dimensions are inclusive of plating 4. dimensions are exclusive of mold flash and metal burr 5. mold flash shall not exceed 0.254mm 6. jedec package reference is mo-193 3.85 max 0.62 max 0.95 ref recommended solder pad layout per ipc calculator 1.4 min 2.62 ref 1.22 ref
lt1800 17 1800fa information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no representa- tion that the interconnection of its circuits as described herein will not infringe on existing patent rights. package description s8 package 8-lead plastic small outline (narrow .150 inch) (reference ltc dwg # 05-08-1610) .016 ?.050 (0.406 ?1.270) .010 ?.020 (0.254 ?0.508) 45 0 ?8 typ .008 ?.010 (0.203 ?0.254) so8 0303 .053 ?.069 (1.346 ?1.752) .014 ?.019 (0.355 ?0.483) typ .004 ?.010 (0.101 ?0.254) .050 (1.270) bsc 1 2 3 4 .150 ?.157 (3.810 ?3.988) note 3 8 7 6 5 .189 ?.197 (4.801 ?5.004) note 3 .228 ?.244 (5.791 ?6.197) .245 min .160 .005 recommended solder pad layout .045 .005 .050 bsc .030 .005 typ inches (millimeters) note: 1. dimensions in 2. drawing not to scale 3. these dimensions do not include mold flash or protrusions. mold flash or protrusions shall not exceed .006" (0.15mm)
lt1800 18 1800fa linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 fax: (408) 434-0507 www.linear.com ? linear technology corporation 2009 lt 0709 rev a ? printed in usa related parts typical application low power high voltage ampli? er certain materials used in optical applications have charac- teristics that change due to the presence and strength of a dc electric ? eld. the voltage applied across these materials should be precisely controlled to maintain desired proper- ties, sometimes as high as 100s of volts. the materials are not conductive and represent a capacitive load. the circuit of figure 6 shows the lt1800 used in an ampli- ? er capable of a 250v output swing and providing precise dc output voltage. when no signal is present, the op amp output sits at about mid-supply. transistors q1 and q3 create bias voltages for q2 and q4, which are forced into a low quiescent current by degeneration resistors r4 and r5. when a transient signal arrives at v in , the op amp output moves and causes the current in q2 or q4 to change depending on the signal polarity. the current, limited by the clipping of the lt1800 output and the 3k of total emitter degeneration, is mirrored to the output devices to drive the capacitive load. the lt1800 output then returns to near mid-supply, providing the precise dc output voltage to the load. the attention to limit the current of the output devices minimizes power dissipation thus allowing for dense layout, and inherits better reliability. figure 7 shows the time domain response of the ampli? er providing a 200v output swing into a 100pf load. figure 6. low power, high voltage ampli? er figure 7. large-signal time domain response of the ampli? er + C lt1800 5v 10k 10k q3 q1 4.99k 1k 1k C130v 1800 f06 4.99k q5 q7 q2 q4 q6 q8 r1 2k r2 2k r5 2k r4 2k r7 2k r6 2k r3 200k 0.1 m f c1 39pf c2 8pf 150v v out v in material under electric field 100pf 130v 5v 5v a v = v out /v in = C100 130v supply i q = 130 m a output swing = 128.8v output offset 20mv output short-circuit current 3ma 10% to 90% rise time 8 m s, 200v output step small-signal bandwidth 150khz q1, q2, q7, q8: on semi mpsa42 q3, q4, q5, q6: on semi mpsa92 1800 f07 10s/div v out 50v/div v in 2v/div part number description comments lt1399 triple 300mhz current feedback ampli? er 0.1db gain flatness to 150mhz, shutdown lt1498/lt1499 dual/quad 10mhz, 6vs rail-to-rail input and output c-load? op amps high dc accuracy, 475v v os(max) , 4mv/c max drift, max supply current 2.2ma per amp lt1630/lt1631 dual/quad 30mhz, 10v/s rail-to-rail input and output op amps high dc accuracy, 525v v os(max) , 70ma output current, max supply current 4.4ma per ampli? er lt1801/lt1802 80mhz, 25v/s low power rail-to-rail input/output precision op amps dual/quad version of the lt1800 lt1806/lt1807 single/dual 325mhz, 140v/s rail-to-rail input and output op amps high dc accuracy, 550v v os(max) , low noise 3.5nv/ hz , low distortion C80db at 5mhz, power-down (lt1806) lt1809/lt1810 single/dual 180mhz rail-to-rail input/output op amps 350v/s slew rate, low distortion Ct at 5mhz, power-down (lt1809) c-load is a trademark of linear technology corporation.

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